Controlling output voltage for power converter

ABSTRACT

A method includes generating a first feedback signal in response to a tracking signal indicating an output signal of the power converter. The method further includes detecting an overshoot of the tracking signal or an undershoot of the tracking signal, generating a second feedback signal in response to the detection result and the first feedback signal, and generating a modulation signal in response to the second feedback signal. A circuit includes an overshoot-and-undershoot (OU) signal generator detecting an overshoot of a tracking signal or an undershoot of the tracking signal. The circuit further includes a feedback signal modulator receiving a first feedback signal and generating a second feedback signal in response to the detection result and the first feedback signal and a modulation controller generating a modulation signal in response to the second feedback signal.

CROSS-REFERENCE TO RELATED APPLICATION

This present disclosure claims the benefit of U.S. ProvisionalApplication No. 62/344,780 filed on Jun. 2, 2016, which is incorporatedby reference herein in its entirety.

BACKGROUND

This present disclosure relates to integrated circuit devices, and moreparticularly to a power converter.

A power converter converts an input voltage into an output voltage andprovides the output voltage to a load. The power converter may regulatethe output voltage at a substantially constant level using a feedbackloop for power factor correction (PFC) control. However, under a loadtransient condition, a relatively narrow bandwidth of the feedback loopmay lead to an overshoot or an undershoot of the output voltage.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 illustrates a power converter according to an embodiment.

FIG. 2 illustrates a power converter suitable for use as the powerconverter of FIG. 1 according to an embodiment.

FIG. 3 illustrates an overshoot-and-undershoot (OU) signal generatorsuitable for use as an OU signal generator of FIG. 2 according to anembodiment.

FIG. 4 illustrates a feedback signal modulator suitable for use as afeedback signal modulator of FIG. 2 according to an embodiment.

FIG. 5A illustrates example waveforms of a first feedback signal, asecond feedback signal, a sampled voltage, an overshoot signal, and anovershoot end signal when an overshoot of an output voltage of the powerconverter of FIG. 2 occurs under a load transient condition.

FIG. 5B illustrates example waveforms of the first feedback signal, asecond feedback signal, the sampled voltage, an undershoot signal, andan undershoot end signal when an undershoot of the output voltage of thepower converter of FIG. 2 occurs under a load transient condition.

FIG. 6 illustrates a feedback signal modulator suitable for use as afeedback signal modulator of FIG. 2 according to an embodiment.

FIG. 7A example waveforms of a first feedback signal, a second feedbacksignal, a sampled voltage, and an overshoot signal when an overshoot ofan output voltage of the power converter of FIG. 2 occurs under a loadtransient condition.

FIG. 7B illustrates example waveforms of the first feedback signal, thesecond feedback signal, the sampled voltage, and an undershoot signalwhen an undershoot of the output voltage of the power converter of FIG.2 occurs under a load transient condition.

FIG. 8 illustrates an OU signal generator suitable for use as the OUsignal generator of FIG. 2 according to an embodiment.

FIG. 9A illustrates example waveforms of a first feedback signal, secondfeedback signals, a sampled voltage, an overshoot signal, and anovershoot end signal when an overshoot of the output voltage of thepower converter of FIG. 2 occurs under a load transient condition.

FIG. 9B illustrates example waveforms of the first feedback signal, thesecond feedback signals, the sampled voltage, an undershoot signal, andan undershoot end signal when an undershoot of the output voltage of thepower converter of FIG. 2 occurs under a load transient condition.

FIG. 10 illustrates a process performed by a controller according to anembodiment.

DETAILED DESCRIPTION

Embodiments relate to power converters and controlling an output signal.In an embodiment, a power converter receives an input voltage andprovides an output voltage to a load. A first feedback signal isgenerated in response to a tracking signal (e.g., a sampled signal),where the tracking signal indicates an output signal of the powerconverter. An overshoot of the sampled signal or an undershoot of thesampled signal is detected, and a second feedback signal is generated inresponse to the detection result and the first feedback signal. Amodulation signal is generated in response to the second feedbacksignal.

FIG. 1 illustrates a power converter 100 according to an embodiment. Thepower converter 100 receives an input voltage V_(IN) and provides anoutput voltage V_(OUT) to a load 160.

The power converter 100 in FIG. 1 includes a primary side controller110. The primary side controller 110 in FIG. 1 may be integrated in asemiconductor chip, and the semiconductor chip may be packaged by itselfor together with one or more other semiconductor chips.

The load 160 in FIG. 1 may include one or more integrated chips (ICs).In an embodiment, the output voltage V_(out) is used to supply power toa Central Processing Unit (CPU), a Graphics Processing Unit (GPU), anintegrated memory circuit, a battery charger, a light emitting diode(LED), or other types of electrical load.

FIG. 2 illustrates a power converter 200 suitable for use as the powerconverter 100 of FIG. 1. The power converter 200 includes a primary sidecircuit 202 and a secondary side circuit 204.

The primary side circuit 202 in FIG. 2 includes a bridge rectifier 206,a capacitor 208, a primary winding 212, a switching device 226, a senseresistor 230, and a primary side controller 210. A power supply (notshown) provides an AC input signal AC_(IN) to the bridge rectifier 206,which inverts the negative halves of the received AC signal to generatea rectified AC signal (or an input voltage) V_(IN). The input voltageV_(IN) is applied to the primary winding 212 of the power converter 200in FIG. 2.

In an embodiment, the primary side controller 210 (e.g., FIG. 2)includes an auxiliary winding 230, first and second resistors 242 and244, a sample-and-hold (S/H) circuit 228, an amplifier 224, anovershoot-and-undershoot (OU) signal generator 220, a feedback signalmodulator 232, a pulse width modulation (PWM) controller (or amodulation controller) 234. The primary side controller 210 in FIG. 2generates a PWM signal (or a modulation signal) PWM to control (e.g.,turn on or off) a switching device 226.

When the switching device 226 in FIG. 2 is turned on, a first currentflowing through the switching device 226 increases from zero to a peakvalue and energy is stored in the primary winding 212. When theswitching device 226 is turned off, the stored energy causes a diode 218in the secondary side circuit 204 to be turned on, resulting in a secondcurrent flowing through the diode 218. During a diode conduction period,a sum of an output voltage V_(OUT) and a diode forward-voltage drop isreflected to the auxiliary winding 230 in FIG. 2 and a magnitude of thesecond current decreases. Because the diode forward-voltage dropdecreases as the second current decreases, the reflected voltage V_(NA)across the auxiliary winding 230 at a time proximate to the end of thediode conduction period can be represented by Equation 1:

$\begin{matrix}{V_{NA} \approx {V_{OUT} \times {\frac{N_{A}}{N_{S}}.}}} & {{Equation}\mspace{14mu} 1}\end{matrix}$In Equation 1, N_(A) is a number of turns of the auxiliary winding 230and N_(S) is a number of turns of the secondary winding 214.

The first and second resistors 242 and 244 in FIG. 2 function as avoltage divider and generate a divided voltage V_(A) at a node betweenthe first and second resistors 242 and 244. The S/H circuit 228 in FIG.2 samples the divided voltage V_(A) at the time proximate to the end ofthe diode conduction period, and thus a tracking signal (e.g., atracking voltage) V_(AOUT) corresponding to the sampled voltage has alevel proportional to that of the output voltage V_(OUT). In anembodiment, the S/H circuit 228 samples the divided voltage V_(A) at thetime corresponding to 70%, 85%, or 90% of the diode conduction period ata previous switching cycle. Although the embodiment shown in FIG. 2includes the S/H circuit 228 to sample the divided voltage V_(A) at aspecific time to generate the sampled voltage V_(AOUT), embodiments ofthe present disclosure are not limited thereto. In an embodiment, theS/H circuit 228 may be omitted, and the divided voltage V_(A) can beused as the tracking signal V_(AOUT) to continuously track the outputvoltage V_(OUT). In another embodiment, the auxiliary winding 230 may befurther omitted, and a scaled version of the output voltage V_(OUT) canbe used as the tracking signal V_(AOUT).

The amplifier 224 in FIG. 2 generates a first feedback signal FB1 inresponse to the sampled voltage V_(AOUT) and a reference voltageV_(REF). In an embodiment, the amplifier 224 is a transconductanceamplifier, which generates a current having a magnitude proportional toa difference between the sampled voltage V_(AOUT) and the referencevoltage V_(REF).

The OU signal generator 220 in FIG. 2 receives the sampled voltageV_(AOUT) and generates an overshoot signal DYN_(OV) and an undershootsignal DYN_(UN) in response to the sampled voltage V_(AOUT).

In an embodiment, the overshoot signal DYN_(OV) transitions from a firstlogic value (e.g., a logic low value) to a second logic value (e.g., alogic high value) when the sampled voltage V_(AOUT) becomes equal to orgreater than an overshoot enable threshold voltage (e.g., an overshootenable threshold voltage V_(OV) _(_) _(EN) in FIG. 3), and transitionsfrom the logic high value to the logic low value when the sampledvoltage V_(AOUT) becomes less than an overshoot disable thresholdvoltage (e.g., an overshoot disable threshold voltage V_(OV) _(_) _(DIS)in FIG. 3). In another embodiment, the overshoot signal DYN_(OV)transitions from a logic low value to a logic high value at a first time(e.g., a first time t₁ in FIG. 9A) when the sampled voltage V_(AOUT)becomes equal to or greater than an overshoot enable threshold voltage,and transitions from the logic high value to the logic low value at asecond time (e.g., a first time t₂ in FIG. 9A) corresponding to a sum ofthe first time and a predetermined time interval.

In an embodiment, the undershoot signal DYN_(UN) transitions from afirst logic value (e.g., a logic low value) to a second logic value(e.g., a logic high value) when the sampled voltage V_(AOUT) becomesless than an undershoot enable threshold voltage (e.g., an undershootenable threshold voltage V_(UN) _(_) _(EN) in FIG. 3), and transitionsfrom the logic high value to the logic low value when the sampledvoltage V_(AOUT) becomes equal to or greater than an undershoot disablethreshold voltage (e.g., an undershoot disable threshold voltage V_(UN)_(_) _(DIS) in FIG. 3). In another embodiment, the undershoot signalDYN_(UN) transitions from a logic low value to a logic high value at afirst time (e.g., a first time t₁ in FIG. 9B) when the sampled voltageV_(AOUT) becomes less than an undershoot enable threshold voltage, andtransitions from the logic high value to the logic low value at a secondtime (e.g., a second time t₂ in FIG. 9B) corresponding to a sum of thefirst time and a predetermined time interval.

The feedback signal modulator 232 in FIG. 2 receives the first feedbacksignal FB1, the overshoot signal DYN_(OV), and the undershoot signalDYN_(UN) to generate a second feedback signal FB2 in response to thereceived signals FB1, DYN_(OV), and DYN_(UN). Although the embodimentshown in FIG. 2 uses the first feedback signal FB1 and the secondfeedback signal FB2, which are analog signals, embodiments of thepresent disclosure are not limited thereto. In an embodiment, ananalog-to-digital converter (not shown) may be added to receive thesampled voltage V_(AOUT) and provide a digital version of the firstfeedback signal FB1 the feedback signal modulator 232. In such anembodiment, the feedback signal modulator 232 generates a digitalversion of the second feedback signal FB2 in response to the receivedsignals FB1, DYN_(OV), and DYN_(UN).

When the overshoot signal DYN_(OV) and the undershoot signal DYN_(UN)have logic low values, respectively, the feedback signal modulator 232generates the second feedback signal FB2 substantially the same as thefirst feedback signal FB1. When either the overshoot signal DYN_(OV) orthe undershoot signal DYN_(UN) has a logic high value, the feedbacksignal modulator 232 generates the second feedback signal FB2 differentfrom the first feedback signal FB1.

The PWM controller 234 in FIG. 2 generates the PWM signal in response tothe second feedback signal FB2. A duty cycle of the PWM signal varieswith a value of the second feedback signal FB2.

In an embodiment, when the overshoot signal DYN_(OV) has a logic highvalue, the second feedback signal FB2 decreases at a faster rate thanthe first feedback signal FB1 to quickly reduce one or both of anon-time duration and a switching frequency of the PWM signal PWM. As aresult, the primary side controller 210 in FIG. 2 may prevent a severeovershoot of the output voltage V_(OUT).

In an embodiment, when the undershoot signal DYN_(UN) has a logic highvalue, the second feedback signal FB2 increases at a faster rate thanthe first feedback signal FB1 to quickly increase one or both of theon-time duration and the switching frequency of the PWM signal PWM. As aresult, the primary side controller 210 in FIG. 2 may prevent a severeundershoot of the output voltage V_(OUT).

FIG. 3 illustrates an OU signal generator 320 suitable for use as the OUsignal generator 220 of FIG. 2 according to an embodiment. The OU signalgenerator 320 in FIG. 3 includes first and second comparators 302 and304, a first flip-flop 306, third and fourth comparators 308 and 310,and a second flip-flop 312.

The first comparator 302 in FIG. 3 compares a sampled voltage V_(AOUT)to an overshoot enable threshold voltage V_(OV) _(_) _(EN), andgenerates a first set signal SET1 having a first logic value (e.g., alogic high value) when the sampled voltage V_(AOUT) is equal to orgreater than the overshoot enable threshold voltage V_(OV) _(_) _(EN).The sampled voltage V_(AOUT) has a magnitude proportional to an outputvoltage (e.g., the output voltage V_(OUT) of FIG. 2) of a powerconverter (e.g., the power converter 200 of FIG. 2).

The second comparator 304 in FIG. 3 compares the sampled voltageV_(AOUT) to an overshoot disable threshold voltage V_(OV) _(_) _(DIS),and generates a first reset signal RST1 having a logic high value whenthe sampled voltage V_(AOUT) is less than the overshoot disablethreshold voltage V_(OV) _(_) _(DIS). The overshoot disable thresholdvoltage V_(OV) _(_) _(DIS) has a level lower than that of the overshootenable threshold voltage V_(OV) _(_) _(EN).

In an embodiment, the first flip-flop 306 in FIG. 3 is a set/reset (RS)flip-flop. The RS flip-flop 306 generates an overshoot signal DYN_(OV)having a first logic value (e.g., a logic high value) when the first setsignal SET1 has a logic high value, and generates the overshoot signalDYN_(OV) having a second logic value (e.g., a logic low value) when thefirst reset signal RST1 has a logic high value. Although the embodimentshown in FIG. 3 includes the first and second comparators 302 and 304and the first flip-flop 306, embodiments of the present disclosure arenot limited thereto. In an embodiment, a single comparator (not shown)having a given hysteresis can replace with the first and secondcomparators 302 and 304 and the first flip-flop 306. For example, thegiven hysteresis makes the comparator generate an overshoot signalDYN_(OV) having a first logic value (e.g., a logic high value) when thesampled voltage V_(AOUT) is equal to or greater than the overshootenable threshold voltage V_(OV) _(_) _(EN) and generate the overshootsignal DYN_(OV) having a second logic value (e.g., a logic low value)when the sampled voltage V_(AOUT) is less than the overshoot disablethreshold voltage V_(OV) _(_) _(DIS).

The third comparator 308 in FIG. 3 compares the sampled voltage V_(AOUT)to an undershoot enable threshold voltage V_(UN) _(_) _(EN), andgenerates a second set signal SET2 having a logic high value when thesampled voltage V_(AOUT) is less than the undershoot enable thresholdvoltage V_(UN) _(_) _(EN).

The fourth comparator 310 in FIG. 3 compares the sampled voltageV_(AOUT) to an undershoot disable threshold voltage V_(UN) _(_) _(DIS),and generates a second reset signal RST2 having a logic high value whenthe sampled voltage V_(AOUT) is equal to or greater than the undershootdisable threshold voltage V_(UN) _(_) _(DIS). The undershoot disablethreshold voltage V_(UN) _(_) _(DIS) has a level higher than that of theundershoot enable threshold voltage V_(UN) _(_) _(EN).

In an embodiment, the second flip-flop 312 in FIG. 3 is a set/reset (RS)flip-flop. The RS flip-flop 312 generates an undershoot signal DYN_(UN)having a first logic value (e.g., a logic high value) when the secondset signal SET2 has a logic high value, and generates the undershootsignal DYN_(UN) having a second logic value (e.g., a logic low value)when the second reset signal RST2 has a logic high value. Although theembodiment shown in FIG. 3 includes the third and fourth comparators 308and 310 and the second flip-flop 312, embodiments of the presentdisclosure are not limited thereto. In an embodiment, a singlecomparator (not shown) having a given hysteresis can replace with thethird and fourth comparators 308 and 310 and the second flip-flop 312.For example, the given hysteresis makes the comparator generate anundershoot signal DYN_(UN) having a first logic value (e.g., a logichigh value) when the sampled voltage V_(AOUT) is less than theundershoot enable threshold voltage V_(UN) _(_) _(EN) and generate theundershoot signal DYN_(UN) having a second logic value (e.g., a logiclow value) when the sampled voltage V_(AOUT) is equal to or greater thanthe undershoot disable threshold voltage V_(UN) _(_) _(DIS).

FIG. 4 illustrates a feedback signal modulator 432 suitable for use asthe feedback signal modulator 232 of FIG. 2 according to an embodiment.The feedback signal modulator 432 in FIG. 4 includes first and secondflip-flops 402 and 422, first and second logic gates 404 and 414, firstand second current sources 406 and 420, an inverter 412, a comparator410, a capacitor 418, first, second, and third switching devices 408,416, and 426, and a third logic gate 424.

The feedback signal modulator 432 in FIG. 4 receives a first feedbacksignal FB1 through an input node I. The input node I is connected to afirst end of the second switching device 416 and to a non-invertinginput of the comparator 410.

The comparator 410 in FIG. 4 has an inverting input receiving a secondfeedback signal FB2 a. The comparator 410 in FIG. 4 compares the firstfeedback signal FB1 to the second feedback signal FB2 a, and generates acomparison signal DYN_(COM).

The first flip-flop 402 in FIG. 4 receives an inverted version of thecomparison signal DYN_(COM) and an inverted version of an overshootsignal DYN_(OV). In an embodiment, the first flip-flop 402 is an RSflip-flop, and the RS flip-flop 402 generates an overshoot end signalOV_(END) having a first logic value (e.g., a logic high value) when theovershoot signal DYN_(OV) has a logic low value, and generates theovershoot end signal OV_(END) having a second logic value (e.g., a logiclow value) when the comparison signal DYN_(COM) has a logic low value.

The first logic gate 404 in FIG. 4 receives the overshoot end signalOV_(END) and an undershoot signal DYN_(UN), and performs a logicaloperation on the received signals OV_(END) and DYN_(UN). In anembodiment, the first logic gate 404 is an OR gate and performs an ORlogical operation on the overshoot end signal OV_(END) and theundershoot signal DYN_(UN) to provide an output signal to the firstswitching device 408.

The first switching device 408 in FIG. 4 is turned on or off in responseto the output signal from the first logic gate 404. In an embodiment,the first switching device 408 is turned on when the output signal fromthe first logic gate 404 has a first logic value (e.g., a logic highvalue), and is turned off when the output signal from the first logicgate 404 has a second logic value (e.g., a logic low value).

The second flip-flop 422 in FIG. 4 receives the comparison signalDYN_(COM) and an inverted version of the undershoot signal DYN_(UN). Inan embodiment, the second flip-flop 422 is an RS flip-flop, and the RSflip-flop 422 generates an undershoot end signal UN_(END) having a firstlogic value (e.g., a logic high value) when the undershoot signalDYN_(UN) has a logic low value, and generates the undershoot end signalUN_(END) having a second logic value (e.g., a logic low value) when thecomparison signal DYN_(COM) has a logic high value.

The second logic gate 414 in FIG. 4 receives the undershoot end signalUN_(END) and the overshoot signal DYN_(OV), and performs a logicaloperation on the received signals UN_(END) and DYN_(OV). In anembodiment, the second logic gate 414 is an OR gate and performs an ORlogical operation on the undershoot end signal UN_(END) and theovershoot signal DYN_(OV) to provide an output signal to the thirdswitching device 426.

The third switching device 426 in FIG. 4 is turned on or off in responseto the output signal from the second logic gate 414. In an embodiment,the third switching device 426 is turned on when the output signal fromthe second logic gate 414 has a first logic value (e.g., a logic highvalue), and is turned off when the output signal from the second logicgate 414 has a second logic value (e.g., a logic low value).

The third logic gate 424 in FIG. 4 receives the overshoot end signalOV_(END), the undershoot end signal UN_(END), the overshoot signalDYN_(OV), and the undershoot signal DYN_(UN). In an embodiment, thethird logic gate 424 is an OR gate and performs an OR logical operationon the received signals OV_(END), UN_(END), DYN_(OV), and DYN_(UN) togenerate a dynamic control signal DYN.

The inverter 412 in FIG. 4 receives the dynamic control signal DYN, andinverts the dynamic control signal DYN to turn on or off the secondswitching device 416. In an embodiment, the second switching device 416is turned on to couple the input node I to an output node O when thedynamic control signal DYN has a logic low value.

The capacitor 418 in FIG. 4 has a first end connected to the output nodeO and a second end connected to a ground. The feedback signal modulator432 in FIG. 4 outputs the second feedback signal FB2 a through theoutput node O. Although the embodiment shown in FIG. 4 includes thecapacitor 418, embodiments of the present disclosure are not limitedthereto. In an embodiment using digital versions of the first feedbacksignal FB1 and the second feedback signal FB2 a, the capacitor 418 maybe replaced with a digital circuit element (e.g., a digital counter).

An operation of a primary side controller (e.g., the primary sidecontroller 210 in FIG. 2), which includes the OU signal generator 320 inFIG. 3 and the feedback signal modulator 432 in FIG. 4, is explainedbelow in more detail below with reference to FIGS. 5A and 5B. FIG. 5Aillustrates example waveforms of the first feedback signal FB1, thesecond feedback signal FB2 a, the sampled voltage V_(AOUT), theovershoot signal DYN_(OV), and the overshoot end signal OV_(END) when anovershoot of an output voltage (e.g., the output voltage V_(OUT) in FIG.2) occurs under a load transient condition.

At a first time t₁ in FIG. 5A, the sampled voltage V_(AOUT) becomesequal to or greater than the overshoot enable threshold voltage V_(OV)_(_) _(EN), and the first flip-flop 306 in FIG. 3 generates an overshootsignal DYN_(OV) having a logic high value in response to the first setsignal SET1 having a logic high value. In an embodiment, the overshootenable threshold voltage V_(OV) _(_) _(EN) has a level equal to orgreater than 110% of a level of a predetermined reference voltageV_(REF). The second logic gate 414 in FIG. 4 generates an output signalhaving a logic high value in response to the overshoot signal DYN_(OV)having a logic high value to turn on the third switching device 426 inFIG. 4. The third logic gate 424 in FIG. 4 generates the dynamic controlsignal DYN having a logic high value in response to the overshoot signalDYN_(OV) having a logic high value to turn off the second switchingdevice 416 in FIG. 4.

During a time interval between the first time t₁ and a second time t₂,the second switching device 416 in FIG. 4 is turned off and the thirdswitching device 426 in FIG. 4 is turned on. A current flowing throughthe second current source 420 in FIG. 4 discharges the capacitor 418 inFIG. 4, and thus a value of the second feedback signal FB2 a isdecreased at a faster rate than the first feedback signal FB1 until thevalue of the second feedback signal FB2 a reaches a minimum value (e.g.,zero volt).

When the value of the second feedback signal FB2 a is decreased, a PWMcontroller (e.g., the PWM controller 234 in FIG. 2) reduces one or bothof an on-time duration and a switching frequency of a PWM signal (e.g.,the PWM signal PWM in FIG. 2). As a result, the primary side controllerincluding the OU signal generator 320 in FIG. 3 and the feedback signalmodulator 432 in FIG. 4 may prevent a severe overshoot of an outputvoltage (e.g., the output voltage V_(OUT) in FIG. 2).

At the second time t₂, the sampled voltage V_(AOUT) becomes less thanthe overshoot disable threshold voltage V_(OV) _(_) _(DIS), and thefirst flip-flop 306 in FIG. 3 generates the overshoot signal DYN_(OV)having a logic low value in response to the first reset signal RET1having a logic high value. In an embodiment, the overshoot disablethreshold voltage V_(OV) _(_) _(DIS) has a level substantially equal to105% of that of the reference voltage V_(REF). As a result, theflip-flop 402 in FIG. 4 generates the overshoot end signal OV_(END)having a logic high value in response to the overshoot signal DYN_(OV)having a logic low value, and the first logic gate 404 in FIG. 4generates an output signal having a logic high value to turn on thefirst switching device 408 in FIG. 4. The third logic gate 424 in FIG. 4generates the dynamic control signal DYN having a logic high value inresponse to the overshoot end signal OV_(END) having a logic high valueto turn off the second switching device 416 in FIG. 4.

During a time interval between the second time t₂ and a third time t₃,the second switching device 416 in FIG. 4 is turned off and the firstswitching device 408 in FIG. 4 is turned on. A current flowing throughthe first current source 406 in FIG. 4 charges the capacitor 418 in FIG.4, and thus a value of the second feedback signal FB2 a is increaseduntil the second feedback signal FB2 a reaches the first feedback signalFB1.

At the third time t₃ when the second feedback signal FB2 a reaches thefirst feedback signal FB1, the comparator 410 in FIG. 4 generates thecomparison signal DYN_(COM) having a logic low value in response to thesecond feedback signal FB2 a and the first feedback signal FB1, and thusthe flip-flop 402 in FIG. 4 generates the overshoot end signal OV_(END)having a logic low value. The third logic gate 424 in FIG. 4 generatesthe dynamic control signal DYN having a logic low value, and thus theinverter 412 in FIG. 4 generates an output signal having a logic highvalue to turn on the second switching device 416 in FIG. 4. As a result,the second switching device 416 in FIG. 4 couples the input node I inFIG. 4 to the output node O in FIG. 4 to generate the second feedbacksignal FB2 a, which is substantially the same as the first feedbacksignal FB1.

FIG. 5B illustrates example waveforms of the first feedback signal FB1,the second feedback signal FB2 a, the sampled voltage V_(AOUT), theundershoot signal DYN_(UN), and the undershoot end signal UN_(END) whenan undershoot of the output voltage occurs under a load transientcondition.

At a first time t₁ in FIG. 5B, the sampled voltage V_(AOUT) becomes lessthan the undershoot enable threshold voltage V_(UN) _(_) _(EN), and thesecond flip-flop 312 in FIG. 3 generates an undershoot signal DYN_(UN)having a logic high value in response to the second set signal SET2having a logic high value. In an embodiment, the undershoot enablethreshold voltage V_(UN) _(_) _(EN) has a level substantially equal toor less than 90% of that of the predetermined reference voltage V_(REF).The first logic gate 404 in FIG. 4 generates an output signal having alogic high value in response to the undershoot signal DYN_(UN) having alogic high value to turn on the first switching device 408 in FIG. 4.The third logic gate 424 in FIG. 4 generates the dynamic control signalDYN having a logic high value in response to the undershoot signalDYN_(UN) having a logic high value to turn off the second switchingdevice 416 in FIG. 4.

During a time interval between the first time t₁ and a second time t₂,the second switching device 416 in FIG. 4 is turned off and the firstswitching device 408 in FIG. 4 is turned on. A current flowing throughthe first current source 406 in FIG. 4 charges the capacitor 418 in FIG.4, and thus a value of the second feedback signal FB2 a is increased ata faster rate than the first feedback signal FB1 until the secondfeedback signal FB2 a reaches a maximum value.

When the value of the second feedback signal FB2 a is increased, the PWMcontroller increases one or both of the on-time duration and theswitching frequency of the PWM signal. As a result, the primary sidecontroller including the OU signal generator 320 in FIG. 3 and thefeedback signal modulator 432 in FIG. 4 may prevent a severe undershootof the output voltage.

At the second time t₂, the sampled voltage V_(AOUT) becomes equal to orgreater than the undershoot disable threshold voltage V_(UN) _(_)_(DIS), and the second flip-flop 312 in FIG. 3 generates the undershootsignal DYN_(UN) having a logic low value in response to the second resetsignal RST2 having a logic high value. In an embodiment, the undershootdisable threshold voltage V_(UN) _(_) _(DIS) has a level substantiallyequal to 95% of that of the predetermined reference voltage V_(REF). Asa result, the flip-flop 422 in FIG. 4 generates the undershoot endsignal UN_(END) having a logic high value in response to the undershootsignal DYN_(UN) having a logic low value, and the second logic gate 414in FIG. 4 generates an output signal having a logic high value inresponse to the undershoot end signal UN_(END) having a logic high valueto turn on the third switching device 426 in FIG. 4. The third logicgate 424 in FIG. 4 generates the dynamic control signal DYN having alogic high value in response to the undershoot end signal UN_(END)having a logic high value to turn off the second switching device 416 inFIG. 4.

During a time interval between the second time t₂ and a third time t₃,the second switching device 416 in FIG. 4 is turned off and the thirdswitching device 426 in FIG. 4 is turned on. A current flowing throughthe second current source 420 in FIG. 4 discharges the capacitor 418 inFIG. 4, and thus a value of the second feedback signal FB2 a isdecreased until the second feedback signal FB2 a reaches the firstfeedback signal FB1.

At the third time t₃ when the second feedback signal FB2 a reaches thefirst feedback signal FB1, the comparator 410 in FIG. 4 generates thecomparison signal DYN_(COM) having a logic high value in response to thesecond feedback signal FB2 a and the first feedback signal FB1, and thusthe flip-flop 422 in FIG. 4 generates the undershoot end signal UN_(END)having a logic low value in response to the comparison signal DYN_(COM)having a logic high value. The third logic gate 424 in FIG. 4 generatesthe dynamic control signal DYN having a logic low value, and thus theinverter 412 in FIG. 4 generates an output signal having a logic highvalue to turn on the second switching device 416. As a result, thesecond switching device 416 in FIG. 4 couples the input node I in FIG. 4to the output node O in FIG. 4 to generate the second feedback signalFB2 a, which is substantially the same as the first feedback signal FB1.

FIG. 6 illustrates a feedback signal modulator 632 suitable for use asthe feedback signal modulator 232 of FIG. 2 according to anotherembodiment. The feedback signal modulator 632 in FIG. 6 includes a logicgate 602, an output node O, and first, second, and third switchingdevices 606, 604, and 608.

The logic gate 602 in FIG. 6 receives an overshoot signal DYN_(OV) andan undershoot signal DYN_(UN). In an embodiment, the logic gate 602 is aNOR gate and performs a NOR logical operation on the overshoot signalDYN_(OV) and the undershoot signal DYN_(UN) to provide an output signalto the second switching device 604.

The second switching device 604 in FIG. 6 is turned on or off inresponse to the output signal from the logic gate 602. In an embodiment,the second switching device 604 is turned on when the output signal fromthe logic gate 602 has a first logic value (e.g., a logic high value),and is turned off when the output signal from the logic gate 602 has asecond logic value (e.g., a logic low value).

The first switching device 606 in FIG. 6 is turned on or off in responseto the undershoot signal DYN_(UN). In an embodiment, the first switchingdevice 606 is turned on when the undershoot signal DYN_(UN) has a firstlogic value (e.g., a logic high value) to couple the output node O to apower supply VDD, and is turned off when the undershoot signal DYN_(UN)has a second logic value (e.g., a logic low value).

The third switching device 608 in FIG. 6 is turned on or off in responseto the overshoot signal DYN_(OV). In an embodiment, the third switchingdevice 608 is turned on when the overshoot signal DYN_(OV) has a firstlogic value (e.g., a logic high value) to couple the output node O to aground, and is turned off when the overshoot signal DYN_(OV) has asecond logic value (e.g., a logic low value).

An operation of a primary side controller (e.g., the primary sidecontroller 210 in FIG. 2), which includes the OU signal generator 320 inFIG. 3 and the feedback signal modulator 632 in FIG. 6, is explainedbelow in more detail below with reference to FIGS. 7A and 7B. FIG. 7Aillustrates example waveforms of the first feedback signal FB1, a secondfeedback signal FB2 b, the sampled voltage V_(AOUT), and the overshootsignal DYN_(OV) when an overshoot of an output voltage (e.g., the outputvoltage V_(OUT) in FIG. 2) occurs under a load transient condition.

At a first time t₁ in FIG. 7A, the sampled voltage V_(AOUT) becomesgreater than the overshoot enable threshold voltage V_(OV) _(_) _(EN),and the first flip-flop 306 in FIG. 3 generates the overshoot signalDYN_(OV) having a logic high value in response to the first set signalSET1 having a logic high value. The logic gate 602 in FIG. 6 generatesan output signal having a logic low value in response to the overshootsignal DYN_(OV) having a logic high value to turn off the secondswitching device 604 in FIG. 6. The third switching device 608 in FIG. 6is turned on in response to the overshoot signal DYN_(OV) having a logichigh value. As a result, the value of the second feedback signal FB2 bis decreased to a minimum value (e.g., zero volt) at the first time t₁,e.g., substantially instantaneously.

At a second time t₂ in FIG. 7A, the sampled voltage V_(AOUT) becomesless than the overshoot disable threshold voltage V_(OV) _(_) _(DIS),and the first flip-flop 306 in FIG. 3 generates the overshoot signalDYN_(OV) having a logic low value in response to the first reset signalRST1 having a logic high value. The third switching device 608 in FIG. 6is turned off in response to the overshoot signal DYN_(OV) having alogic low value. The logic gate 602 in FIG. 6 generates the outputsignal having a logic high value in response to the overshoot signalDYN_(OV) having a logic low value to turn on the second switching device604 in FIG. 6. As a result, the second feedback signal FB2 b reaches thefirst feedback signal FB1 at the second time t₂, e.g., substantiallyinstantaneously.

FIG. 7B illustrates example waveforms of the first feedback signal FB1,the second feedback signal FB2 b, the sampled voltage V_(AOUT), and theundershoot signal DYN_(UN) when an undershoot of the output voltageoccurs under a load transient condition.

At a first time t₁ in FIG. 7B, the sampled voltage V_(AOUT) becomes lessthan the undershoot enable threshold voltage V_(UN) _(_) _(EN), and thesecond flip-flop 312 in FIG. 3 generates an undershoot signal DYN_(UN)having a logic high value in response to the second set signal SET2having a logic high value. The logic gate 602 in FIG. 6 generates theoutput signal having a logic low value in response to the undershootsignal DYN_(UN) having a logic high value to turn off the secondswitching device 604 in FIG. 6. The first switching device 606 in FIG. 6is turned on in response to the undershoot signal DYN_(UN) having alogic high value. As a result, the value of the second feedback signalFB2 b is increased to a maximum value (e.g., the power supply voltageVDD) at the first time t₁, e.g., substantially instantaneously.

At a second time t₂ in FIG. 7B, the sampled voltage V_(AOUT) becomesequal to or greater than the undershoot disable threshold voltage V_(UN)_(_) _(DIS), and the second flip-flop 312 in FIG. 3 generates theundershoot signal DYN_(UN) having a logic low value in response to thesecond reset signal RST2 having a logic high value. The first switchingdevice 606 in FIG. 6 is turned off in response to the undershoot signalDYN_(UN) having a logic low value. The logic gate 602 in FIG. 6generates the output signal having a logic high value to turn on thesecond switching device 604 in FIG. 6. As a result, the second feedbacksignal FB2 b reaches the first feedback signal FB1 at the second timet₂, e.g., substantially instantaneously.

FIG. 8 illustrates an OU signal generator 820 suitable for use as the OUsignal generator 220 of FIG. 2 according to another embodiment. The OUsignal generator 820 in FIG. 8 includes a first comparator 802, a firstdelay circuit 806, a first flip-flop 804, a second comparator 808, asecond delay circuit 812, and a second flip-flop 810.

The first comparator 802 in FIG. 8 compares a sampled voltage V_(AOUT)to an overshoot enable threshold voltage V_(OV) _(_) _(EN), andgenerates a first output signal OUT1 having a logic high value when thesampled voltage V_(AOUT) is equal to or greater than the overshootenable threshold voltage V_(OV) _(_) _(EN). The first delay circuit 806in FIG. 8 delays the first output signal OUT1 by a first delay amount togenerate a delayed version of the first output signal OUT1.

In an embodiment, the first flip-flop 804 in FIG. 8 is a set/reset (RS)flip-flop. The RS flip-flop 804 generates an overshoot signal DYN_(OV)having a first logic value (e.g., a logic high value) when the firstoutput signal OUT1 has a logic high value, and generates the overshootsignal DYN_(OV) having a second logic value (e.g., a logic low value)when the delayed version of the first output signal OUT1 has a logichigh value. As a result, the RS flip-flop 804 generates a pulse having awidth that corresponds to the first delay amount of the first delaycircuit 806.

The second comparator 808 in FIG. 8 compares the sampled voltageV_(AOUT) to an undershoot enable threshold voltage V_(UN) _(_) _(EN),and generates a second output signal OUT2 having a logic high value whenthe sampled voltage V_(AOUT) is less than the undershoot enablethreshold voltage V_(UN) _(_) _(EN). The second delay circuit 808 inFIG. 8 delays the second output signal OUT2 by a second delay amount togenerate a delayed version of the second output signal OUT2.

In an embodiment, the second flip-flop 810 in FIG. 8 is a set/reset (RS)flip-flop. The RS flip-flop 810 generates an undershoot signal DYN_(UN)having a first logic value (e.g., a logic high value) when the secondoutput signal OUT2 has a logic high value, and generates the undershootsignal DYN_(UN) having a second logic value (e.g., a logic low value)when the delayed version of the second output signal OUT2 has a logichigh value. As a result, the RS flip-flop 810 generates a pulse having awidth that corresponds to the second delay amount of the second delaycircuit 810.

FIG. 9A illustrates an operation of a primary side controller (e.g., theprimary side controller 210 in FIG. 2), which includes the OU signalgenerator 820 in FIG. 8 and the feedback signal modulator 432 in FIG. 4or includes the OU signal generator 820 in FIG. 8 and the feedbacksignal modulator 632 in FIG. 6. Specifically, FIG. 9A illustratesexample waveforms of the first feedback signal FB1, the second feedbacksignals FB2 a and FB2 b, the sampled voltage V_(AOUT), the overshootsignal DYN_(OV), and the overshoot end signal OV_(END) when an overshootof an output voltage (e.g., the output voltage V_(OUT) in FIG. 2) occursunder a load transient condition.

Unlike the OU signal generator 320 in FIG. 3 including the secondcomparator 304, the OU signal generator 820 in FIG. 8 includes the firstdelay circuit 806. As a result, a time interval between a first time t₁and a second time t₂ in FIG. 9A is determined by the first delay amountof the first delay circuit 806 in FIG. 8, rather than by a comparisonresult of the second comparator 304 in FIG. 3. Other operations of theOU signal generator 820 in FIG. 8 are similar to those of the OU signalgenerator 320 in FIG. 3, and thus detailed descriptions of theseoperations of the primary side controller including the OU signalgenerator 820 in FIG. 8 will be omitted herein for the interest ofbrevity.

FIG. 9B illustrates an operation of the primary side controller, whichincludes the OU signal generator 820 in FIG. 8 and the feedback signalmodulator 432 in FIG. 4 or includes the OU signal generator 820 in FIG.8 and the feedback signal modulator 632 in FIG. 6. Specifically, FIG. 9Billustrates example waveforms of the first feedback signal FB1, thesecond feedback signals FB2 a and FB2 b, the sampled voltage V_(AOUT),the undershoot signal DYN_(UN), and the undershoot end signal UN_(END)when an undershoot of an output voltage (e.g., the output voltageV_(OUT) in FIG. 2) occurs under a load transient condition.

Unlike the OU signal generator 320 in FIG. 3 including the fourthcomparator 312, the OU signal generator 820 in FIG. 8 includes thesecond delay circuit 812. As a result, a time interval between a firsttime t₁ and a second time t₂ in FIG. 9B is determined by the seconddelay amount of the second delay circuit 812 in FIG. 8, rather than by acomparison result of the fourth comparator 312 in FIG. 3. Otheroperations of the OU signal generator 820 in FIG. 8 are similar to thoseof the OU signal generator 320 in FIG. 3, and thus detailed descriptionsof these operations of the primary side controller including the OUsignal generator 820 in FIG. 8 will be omitted herein for the interestof brevity.

FIG. 10 illustrates a process 1000 performed by a controller (e.g., theprimary side controller 210 of FIG. 2) according to an embodiment. In anembodiment, the controller includes an OU signal generator (e.g., the OUsignal generator circuit 220 of FIG. 2), a feedback signal modulator(e.g., the feedback signal modulator 232 of FIG. 2), and a modulationcontroller (e.g., the PWM controller 234 of FIG. 2).

At S1020, the controller generates a first feedback signal (e.g., thefirst feedback signal FB1 of FIG. 2) in response to a sampled signal(e.g., the sampled signal V_(AOUT) of FIG. 2), which indicates an outputsignal of a power converter (e.g., the power converter 200 of FIG. 2).In an embodiment, the controller further includes an amplifier (e.g.,the amplifier 224 of FIG. 2) that generates the first feedback signal inresponse to the sampled signal and a reference voltage (e.g., thereference voltage V_(REF) of FIG. 2).

At S1040, the OU signal generator detects an overshoot or an undershootof the sampled signal. In an embodiment, the OU signal generatorgenerates an overshoot signal having a first logic value (e.g., a logichigh value) when the overshoot is detected, and generates an undershootsignal having a second logic value (e.g., a logic high value) when theundershoot is detected. In an embodiment, the first and second logicvalues are the same values, but may be different values in otherembodiments.

At S1060, the feedback signal modulator generates a second feedbacksignal (e.g., the second feedback signal FB2 of FIG. 2) in response tothe detection result and the first feedback signal. In an embodiment,the feedback signal modulator generates the second feedback signal thatis different from the first feedback signal when the OU signal generatordetects the overshoot of the sampled signal or the undershoot of thesampled signal.

At S1080, the modulation controller generates a modulation signal (e.g.,the PWM signal PWM of FIG. 2) in response to the second feedback signal.In an embodiment, the modulation controller adjusts one or both of anon-time duration and a switching frequency of the modulation signal inresponse to the second feedback signal.

Aspects of the present disclosure have been described in conjunctionwith the specific embodiments thereof that are proposed as examples.Numerous alternatives, modifications, and variations to the embodimentsas set forth herein may be made without departing from the scope of theclaims set forth below. Accordingly, embodiments as set forth herein areintended to be illustrative and not limiting.

What is claimed is:
 1. A method for controlling a power converter, themethod comprising: generating a first feedback signal in response to atracking signal, the tracking signal indicating an output signal of thepower converter; detecting an overshoot of the tracking signal or anundershoot of the tracking signal; generating a second feedback signalin response to a detection result and the first feedback signal; andgenerating a modulation signal in response to the second feedbacksignal, wherein the second feedback signal is substantially the same asthe first feedback signal when neither the overshoot nor the undershootis detected, and wherein the second feedback signal changes at a ratefaster than a rate of the first feedback signal when the overshoot orthe undershoot is detected.
 2. The method of claim 1, furthercomprising: comparing a value of the tracking signal to a value of anovershoot enable threshold voltage; generating an overshoot signalhaving a first logic value when a first comparison result is obtainedfrom comparing the value of the tracking signal to the value of theovershoot enable threshold voltage; comparing the value of the trackingsignal to a value of an overshoot disable threshold voltage; andgenerating the overshoot signal having a second logic value when asecond comparison result is obtained from comparing the value of thetracking signal to the value of the overshoot disable threshold voltage.3. The method of claim 2, further comprising: decreasing a value of thefirst feedback signal at a first rate; and decreasing a value of thesecond feedback signal at a second rate in response to the overshootsignal having the first logic value, the second rate being higher thanthe first rate of the first feedback signal, wherein the firstcomparison result is obtained when the value of the tracking signal isequal to or greater than the value of the overshoot enable thresholdvoltage, and the second comparison result is obtained when the value ofthe tracking signal is less than the value of the overshoot disablethreshold voltage.
 4. The method of claim 2, further comprising:generating an overshoot end signal having the first logic value inresponse to the overshoot signal having the second logic value;increasing a value of the second feedback signal until the value of thesecond feedback reaches a value of the first feedback signal; andgenerating the overshoot end signal having the second logic value whenthe value of the second feedback signal reaches the value of the firstfeedback signal.
 5. The method of claim 1, further comprising: comparinga value of the tracking signal to a value of an undershoot enablethreshold voltage; generating an undershoot signal having a first logicvalue when a first comparison result is obtained from comparing thevalue of the tracking signal to the value of the undershoot enablethreshold voltage; comparing the value of the tracking signal to a valueof an undershoot disable threshold voltage; and generating theundershoot signal having a second logic value when a second comparisonresult is obtained from comparing the value of the tracking signal tothe value of the undershoot disable threshold voltage.
 6. The method ofclaim 5, further comprising: increasing a value of the first feedbacksignal at a first rate; and increasing a value of the second feedbacksignal at a second rate when the undershoot signal has the first logicvalue, the second rate being higher than the first rate of the firstfeedback signal, wherein the first comparison result obtained is whenthe value of the tracking signal is less than and the value of theundershoot enable threshold voltage, and the second comparison result isobtained when the value of the tracking signal is equal to or greaterthan the value of the undershoot disable threshold voltage.
 7. Themethod of claim 5, further comprising: generating an undershoot endsignal having the first logic value in response to the undershoot signalhaving the second logic value; decreasing a value of the second feedbacksignal until the value of the second feedback reaches a value of thefirst feedback signal; and generating the undershoot end signal havingthe second logic value when the value of the second feedback signalreaches the value of the first feedback signal.
 8. A circuit forcontrolling a power converter comprising: an overshoot-and-undershoot(OU) signal generator configured to detect an overshoot of a trackingsignal or an undershoot of the tracking signal, the tracking signalindicating an output signal of the power converter; a feedback signalmodulator configured to receive a first feedback signal and generate asecond feedback signal in response to a detection result and the firstfeedback signal; and a modulation controller configured to generate amodulation signal in response to the second feedback signal, wherein thefeedback signal modulator generates the second feedback signal that issubstantially the same as the first feedback signal when neither theovershoot nor the undershoot is detected, and wherein the feedbacksignal modulator changes the second feedback signal at a rate fasterthan a rate of the first feedback signal when the OU signal generatordetects the overshoot or the undershoot.
 9. The circuit of claim 8,wherein the OU signal generator includes: a comparator comparing a valueof the tracking signal to a value of an overshoot enable thresholdvoltage and a value of an overshoot disable threshold voltage, thecomparator generating an overshoot signal having a first logic valuewhen a first comparison result is obtained and generating the overshootsignal having a second logic value when a second comparison result isobtained.
 10. The circuit of claim 9, further comprising: an amplifierdecreasing a value of the first feedback signal at a first rate, whereinthe comparator includes: a first comparator comparing the value of thetracking signal to the value of the overshoot enable threshold voltage;a second comparator comparing the value of the tracking signal to thevalue of the overshoot disable threshold voltage; and a first flip-flopgenerating the overshoot signal having the first logic value when thefirst comparator outputs the first comparison result, and generating theovershoot signal having the second logic value when the secondcomparator outputs the second comparison result, wherein the feedbacksignal modulator includes: a capacitor having a first end connected to aground and a second end connected to an output node; a first currentsource discharging the capacitor to decrease a value of the secondfeedback signal at a second rate in response to the overshoot signalhaving the first logic value, the second rate being higher than thefirst rate of the first feedback signal; and a first switching devicecoupling the capacitor to the first current source in response to theovershoot signal having the first logic value, and wherein the firstcomparator outputs the first comparison result when the value of thetracking signal is equal to or greater than the value of the overshootenable threshold voltage, and the second comparator outputs the secondcomparison result when the value of the tracking signal is less than thevalue of the overshoot disable threshold voltage.
 11. The circuit ofclaim 10, wherein the feedback signal modulator further includes: asecond flip-flop generating an overshoot end signal having the firstlogic value in response to the overshoot signal having the second logicvalue; a second current source charging the capacitor to increase thevalue of the second feedback signal until the value of the secondfeedback reaches the value of the first feedback signal; and a secondswitching device coupling the capacitor to the second current source inresponse to the overshoot end signal having the first logic value, andwherein the second flip-flop generates the overshoot end signal havingthe second logic value when the value of the second feedback signalreaches the value of the first feedback signal.
 12. The circuit of claim8, wherein the OU signal generator includes: a comparator comparing avalue of the tracking signal to a value of an undershoot enablethreshold voltage and a value of an undershoot disable thresholdvoltage, the comparator generating an undershoot signal having a firstlogic value when a first comparison result is obtained and generatingthe undershoot signal having a second logic value when a secondcomparison result is obtained.
 13. The circuit of claim 12, furthercomprising: an amplifier increasing a value of the first feedback signalat a first rate, wherein the comparator includes: a first comparatorcomparing the value of the tracking signal to the value of theundershoot enable threshold voltage; a second comparator comparing thevalue of the tracking signal to the value of the undershoot disablethreshold voltage; and a first flip-flop generating an undershoot signalhaving the first logic value when the first comparator outputs the firstcomparison result, and generating the undershoot signal having thesecond logic value when the second comparator outputs the secondcomparison result, wherein the feedback signal modulator includes: acapacitor having a first end connected to a ground and a second endconnected to an output node; a first current source charging thecapacitor to increase a value of the second feedback signal at a secondrate when the undershoot signal has the first logic value, the secondrate being higher than the first rate of the first feedback signal; anda first switching device coupling the capacitor to the first currentsource in response to the undershoot signal having the first logicvalue, and wherein the first comparator outputs the first comparisonresult when the value of the tracking signal is less than the value ofthe undershoot enable threshold voltage, and the second comparatoroutputs the second comparison result when the value of the trackingsignal is equal to or greater than the value of the undershoot disablethreshold voltage.
 14. The circuit of claim 13, wherein the feedbacksignal modulator further includes: a second flip-flop generating anundershoot end signal having the first logic value in response to theundershoot signal having the second logic value; a second current sourcedischarging the capacitor to decrease the value of the second feedbacksignal until the value of the second feedback reaches the value of thefirst feedback signal; and a second switching device coupling thecapacitor to the second current source in response to the undershoot endsignal having the first logic value, and wherein the second flip-flopgenerates the undershoot end signal having the second logic value whenthe value of the second feedback signal reaches the value of the firstfeedback signal.
 15. A power converter comprising: a primary sidecircuit generating an input signal; and a secondary side circuitgenerating an output signal in response to the input signal, wherein theprimary side circuit including: a switching device; and a primary sidecontroller configured to detect an overshoot of the output signal or anundershoot of the output signal and generate a first feedback signal inresponse to a tracking signal, the tracking signal indicating the outputsignal, the primary side controller generating a second feedback signalin response to a detection result and the first feedback signal andgenerating a modulation signal in response to the second feedback signalto control the switching device, the second feedback signal beingdifferent from the first feedback signal when the overshoot or theundershoot is detected, the second feedback signal being substantiallythe same as the first feedback signal when neither the overshoot nor theundershoot is detected, wherein the primary side controller changes thesecond feedback signal at a rate faster than a rate of the firstfeedback signal when the primary side controller detects the overshootor the undershoot.